UBM Tech

# A simple software lowpass filter suits embedded-system applications

By Barry L Dorr, Dorr Engineering - May 25, 2006

Hardware-design engineers have long recognized the usefulness of RC lowpass filters (Figure 1). Lowpass filters are useful for performing signal conditioning, removing noise from a signal, or rejecting unwanted signals. The first-order recursive filter is the digital equivalent of the RC filter, and, as the ratio of the sample frequency to the bandwidth increases, their responses become identical.

All lowpass filters produce a weighted average of the current input value and past inputs. A filter's characteristics depend on the weighting used for the past inputs. For example, a lowpass filter (Figure 2) smoothes noisy input signals. One possibility for weighting the past-input samples is to give them equal weight. Although this approach produces a useful lowpass filter, it makes more intuitive sense to weigh newer samples more heavily than older samples.

A designer can use recursion to implement a weighting function (Figure 3). This approach minimizes the processing impact of the multiplications in this filter because the designer can implement the multiplications as left or rights shifts in the software. The designer feeds data samples with bit width B1 into the filter at a fixed sample rate. Bit width B2 may be larger than bit width B1. The summing block adds the input sample to the last output sample, and the delay is a digital delay of one sample. The parameter k is a shift value that controls the filter bandwidth. Mathematically, the recursion in Figure 3 is: y(n)=(1-2–k)×y(n–1)+x(n), where x is the input, y is the output, and n is the sample index.

As an example of filter operation, suppose that k=4 so 1–2–k =0.9375, the value at the delay output is zero, and the filter input is a single sample of one followed by all zeros. If you use the summing block as the output, the first output from the filter is one. When you feed this output back to the summing block, the multiplier scales it, and it becomes 0.9375. The next output is 0.93752 or 0.8789, and the nth output is 0.9375n. This sequence is the impulse response of the filter, but it is also the weighting function (Figure 4). Good stuff is going on here for those who like math, but we'll stick to the implementation.

## Specifying the filter response

A designer can specify the filter response in either the frequency domain or the time domain. Which one to use depends on the type of problem you are working on. If noise or unwanted tones are the problems, then the frequency-domain specification or bandwidth is appropriate. To reject impulse-noise hits, or smooth measured data, the time-domain specification or rise time may work better.

When working in the frequency domain, the designer specifies the 3-dB frequency or bandwidth of the filter. At this frequency, the amplitude of the output drops to 0.707 times the amplitude that a dc signal causes (Figure 5a). You can estimate the attenuation at higher frequencies because doubling the frequency approximately halves the amplitude. Table 1, which is normalized to a sample rate of 1 Hz, shows the normalized bandwidth and rise time for several values of k. To get the actual bandwidth, multiply the value in the table by the sampling frequency.

When working in the time domain, the designer specifies the rise time of the output in response to a step input. Figure 5b shows the filter output when the input changes from all zeros to all ones, which causes the output to gradually move from zero to one. The rise time is the time necessary for the filter output to move from 10 to 90% of the final value. Table 1 specifies the rise time in number of samples.

Before writing code to implement this filter, the designer must specify the number of bits necessary for the summing block and the delay. Because the filter is basically an averaging device, the range of the summing-block output is larger than the range of the input signal if there is to be no loss in precision. Fortunately, it is easy to predict the growth in the output-register width because the dc gain from the input to the summing-block output is 2k, so bit width B2 from Figure 2 is k bits wider than bit width B1. You can maintain a unity gain by multiplying the summing-block output by 2–k.

The fixed-point code in Listing 1 implements a filter for the case of k=4. Using a power of two for k enables the use of right shifts in the code to avoid the performance hit from the multiplier blocks. Using a 32-bit integer for the summing block and delay accommodates the four bits of growth in the output register. When using this code, make sure that your compiler sign extends when right-shifting a signed number.

The first-order recursive filter, or "leaky integrator," is a simple yet powerful filter that is a time-tested approach for many filtering applications, and this implementation requires no multiply instructions. The steps to quickly and accurately implement this filter are to specify the filter using either the rise time or the bandwidth, allocate k additional bits for the summing block and delay to accommodate register growth, and implement the filter by substituting shifts instead of multiply instructions as the example code shows.

KNOWLEDGE CENTER